Bus line current calibration

ABSTRACT

Disclosed herein is a method and system for calibrating line drive currents in systems that generate data signals by varying line drive currents and that interpret the data signals by comparing them to one or more reference voltages. The calibration includes varying the line drive current at a transmitting component. At different line drive currents, a receiver reference voltage is varied while the transmitting component transmits data to a receiving component. At each line drive current, the system records the highest and lowest receiver reference voltages at which data errors do not occur. The system then examines the recorded high and low receiver reference voltages to determine a desirable line drive current.

CROSS-REFERENCE(S) TO RELATED APPLICATION(S)

This U.S. patent application is a continuation patent application of co-pending prior application Ser. No. 11/068,260 filed on 28 Feb. 2005, which is a continuation of prior application Ser. No. 10/409,033 filed on 8 Apr. 2003, now U.S. Pat. No. 6,988,044, which is a continuation of co-pending prior application Ser. No. 09/711,606, filed on 13 Nov. 2000 (now U.S. Pat. No. 6,546,343, issued on 8 Apr. 2003), U.S. patent application Ser. Nos. 09/711,606, 10/409,033, and 11/068,260 are hereby incorporated by reference in their entirety herein.

TECHNICAL FIELD

This invention relates to bus systems in which line voltages are generated by varying line currents and are interpreted with reference to a reference voltage.

BACKGROUND OF THE INVENTION

FIG. 1 is a block diagram showing a high-speed digital computer bus system 20. The bus system includes a number of discrete devices 22–24, which communicate over an electrical bus 25 at very high speeds. The bus includes a plurality of data transmission lines.

This system includes a master device 22 and a plurality of slave devices 23–24. The master device 22 initiates and controls data exchanges over bus 25. During a data exchange, any one of devices 22–24 can act as either a transmitting component or a receiving component. Generally, there is only one transmitting component during any single data exchange. However, there can be one or a plurality of receiving components during a data exchange.

FIG. 2 illustrates the configuration and operation of a single bus line 26 between a transmitting component 27 and a receiving component 28. The bus line is terminated at one end to a termination voltage V_(term) through a termination impedance R_(term). Transmitting component 27 has a line current driver 29, which produces line voltages with specified relationships to a reference voltage VREF.

More specifically, driver 29 is a current source or sink that creates desired voltage drops across termination impedance R_(term). The current driver 29 is turned on or otherwise enabled to produce one logic level voltage, and is turned off or otherwise disabled to produce another logic level voltage. In actual embodiment, the current driver 29 sinks current when enabled, and does not sink or source current when disabled. When disabled, the line voltage is approximately equal to V_(term). When enabled, the line voltage is lower than V_(term), because of a voltage drop through termination impedance R_(term).

As an example, suppose that V_(term) is 2.5 volts. When driver 29 is disabled there is no current through the bus line, and the bus line voltage is equal to V_(term), or 2.5 volts. This is the high logic level, and is referred to as V_(OH). On the other hand, when driver 29 is enabled the current through the bus line drops the line voltage to a lower value V_(OL), which in this example is 1.9 volts. V_(OL) is the low logic level.

The voltage difference between V_(OH) and V_(OL), also referred to as a line voltage swing V_(swing), is controlled by the value of termination resistance V_(term) and the amount of line current I_(O) (which is controlled by the current driver 29). It is desirable to limit the line voltage swing as much as possible to enable higher bus speeds. If the voltage swing is too small, however, a receiving component will not be able to reliably distinguish between high and low logic level voltages.

FIG. 2 also illustrates how the line voltage is interpreted at receiving component or device 28. Specifically, the received line voltage V_(O) is compared to reference voltage VREF by a comparator 40. If V_(O) is greater than VREF, the line voltage represents a high logic level. If V_(O) is less than VREF, the line voltage represents a low logic level.

For this determination to be valid, the transmitting component needs to set its V_(OH) and V_(OL) relative to VREF. Preferably, V_(OH) and V_(OL) are established symmetrically around VREF. In the example of FIG. 3, V_(OH) is 2.5 volts, V_(REF) is 2.2 volts, and V_(OL) is 1.9 volts. This yields a 0.6 volt voltage swing: 0.3 volts on either side of VREF.

FIG. 3 shows a circuit for creating a symmetrical voltage swing around VREF during a calibration process. This circuit, which is used only during the calibration, utilizes two different bus lines 60 and 61, each of which are similar to the bus line 26 shown in FIG. 2.

The calibration circuit has current drivers 62 and 63, and a current control 64 which in this case is an up/down counter. Current drivers 62 and 63 are switched on and off by data control lines (not shown) to create high and low voltage levels V_(OH) and V_(OL) on the corresponding bus lines. When a driver is on, the magnitude of its output current is determined by the value contained in up/down counter 64.

Bus lines 60 and 61 extend to receiving components and a termination resistor (not shown). Within the transmitting component, however, the high and low output voltages V_(OH) and V_(OL) are sampled for purposes of adjusting the current driver outputs to create a symmetric voltage swing. Specifically, a simple R over R resistive voltage divider 66 is placed between a line producing a high logic voltage V_(OH) and another line producing a low logic level V_(OL). In this case, it is assumed that line 60 is at the high voltage level, with current driver 62 inactive; and bus line 61 is at the low voltage level, with current driver 63 being active. Furthermore, the resistive divider 66 is configured to produce an intermediate output voltage V_(I) that is equal to (V_(OH)+V_(OL))/2. For symmetry around VREF, V_(I) should be equal to VREF. A feedback system is used to minimize the voltage difference between V_(I) and VREF. Both V_(I) and VREF are connected to the inputs of a comparator 68, which produces a logic voltage V_(F) that is high when V_(I)−VREF>0, and low when V_(I)−VREF<0. V_(F) is then connected to counter 64. The output of the counter, in turn, is connected to control the output of current drivers 62 and 63.

The circuit works as follows. During calibration, counter 64 is enabled and/or clocked, and repetitively adjusts its output either up or down depending on the logic value of V_(F). This increases or decreases the output of current driver 63. The output current is thus adjusted until the value of counter 64 has settled. At this point, V_(I)−VREF=zero—meaning that V_(I)=VREF and that V_(OH) and V_(OL) are symmetric around VREF. At this point, the value of counter 64 is frozen until the next calibration (although minor adjustments might be made by temperature control circuits).

In most cases, this calibration is performed at system initialization. Optionally, the calibrated current control value (from the counter) can be stored in a current control register and used during normal bus operation to control the magnitude of I_(O). This value can then be subject to temperature correction circuits to determine the current control value at any given time. Alternatively, the calibration can be performed periodically to account for temperature and voltage variations.

Ideally, both the transmitting component and a receiving component have the same value of VREF. In practice, however, this can be difficult to achieve due to signal line losses and/or noise. Accordingly, VREF at the receiving component is often somewhat different than VREF at the transmitting component. Furthermore, V_(OH) and V_(OL) often change as they propagate through the signal line, again due to losses and noise. Thus, the relationship between V_(OH), V_(OL) and VREF may not be the same at the transmitting component as it is at the receiving component. In other words, V_(swing) might not be symmetric around VREF by the time the signals reach a receiving component.

In the bus configuration described above, line losses generally affect V_(OL) more than V_(OH). At V_(OL), the voltage is being produced by a current through the bus line, so the voltage can be affected along the length of the bus line by resistive and capacitive loads. At V_(OH), however, there is no line current, and therefore less opportunity for the voltage to be affected along the length of the bus line. This situation affects both the line voltage swing and the relationship of V_(OL) with VREF.

The non-symmetry at the receiving component has negative effects. If V_(OL) is higher at the receiving component, the voltage margin from VREF to V_(OL) is decreased. When V_(OL) is lower at the receiving component, low-side margin is increased, but the higher V_(swing) would cause more reflections, which could degrade the high-side margin during a subsequent data transfer cycle.

This issue has been addressed by introducing a degree of asymmetry at the transmitting component in order to provide symmetry at the receiving component: the current drivers at the transmitting component are adjusted to achieve voltage symmetry at the receiving component. The amount of asymmetry at the transmitting component is referred to as the overdrive factor (ODF).

A desired asymmetry at the transmitting component can be created by varying the ratio of voltage divider 66. Thus, instead of producing a signal V_(I) that is 50% of the way from V_(OL) to V_(OH), the resistors can be chosen to implement any other percentage. This creates asymmetry at the transmitting component to correct for any asymmetry that would otherwise be present at the receiving component.

In actual embodiment, the ratio of voltage divider 66 has been controlled by a symmetry control register. Different values can be loaded into the symmetry control register to create different degrees of asymmetry at the transmitting component. Symmetry control values can be stored for a plurality of different receivers, and used when transmitting to those receivers. This accounts for variations in conditions at different receivers.

In some such circuits, the value of counter 64 is stored after completion of the calibration process, and loaded into a current control register during actual operation. A plurality of values can be stored, corresponding to different receiving components. The current control register is reloaded for communication with different receiving components.

The desired line current and corresponding divider percentage or ratio are determined during system design—prior to manufacture of the transmitting component or prior to manufacture of a circuit that utilizes the transmitting component. The determination is based on testing and/or simulating, and choosing voltage divider ratios that are predicted to work with the different receivers in light of the actual circuit layout. In some cases, the transmitting component includes logic for predicting required asymmetry values based on known system parameters such as distances between components.

The inventors, however, have discovered and developed a way to dynamically determine appropriate line drive currents at system initialization, based on tested characteristics of the circuits themselves.

BRIEF DESCRIPTION OF THE DRAWINGS

FIG. 1 is a block diagram of a high-speed digital computer bus system in accordance with the prior art.

FIG. 2 is a block diagram illustrating a bus line transmitter and receiver in accordance with the prior art.

FIG. 3 is a block diagram illustrating a prior art method of controlling bus line current.

FIG. 4 is a block diagram of a first embodiment illustrating a bus line calibration method.

FIG. 5 is a flowchart showing methodological operations performed in a bus line calibration method.

FIG. 6 is a block diagram of a second embodiment illustrating a bus line calibration method.

DETAILED DESCRIPTION

The following description sets forth specific embodiments of a bus driver calibration method and circuits having elements recited in the appended claims. The embodiment is described with specificity in order to meet statutory requirements. However, the description itself is not intended to limit the scope of this patent. Rather, the inventors have contemplated that the claimed invention might also be embodied in other ways, to include different elements or combinations of elements similar to the ones described in this document, in conjunction with other present or future technologies.

FIG. 4 shows pertinent parts of a data communications system 100 that can be used to implement a method of calibrating or finding a desirable line drive current. The system allows such calibration during device operation. The calibration is usually performed at system startup or initialization. Through actual testing during the calibration procedure, asymmetry values are determined for different transmitting components. Furthermore, each transmitting component can find a different asymmetry value for every possible receiving component. This allows an optimal line current to be used for each different receiver.

The overall system is of a type that interprets data signals by comparing them to reference voltages. Signals are transmitted over a plurality of data is signaling lines, also referred to as bus lines. Each bus line is terminated to a termination voltage V_(term), through a termination resistance R_(term). The data signals comprise line voltages that are produced by line drive currents through R_(term). The line voltages are compared to the reference voltages to determine whether the voltages represent high or low logic values.

This type of bus system is used in various environments. One of its most common uses is for high-speed data communications busses between microprocessors and peripheral devices such as high-speed memory devices. Such bus systems are also used in high-speed memory subsystems, between memory devices and memory device controllers.

For purposes of discussion, the illustration of FIG. 4 has been greatly simplified, and shows only parts of the transmitting and receiving components that might be used in a calibration process.

FIG. 4 shows a single transmitting component 102 and a single receiving component 104. A data bus line 106 extends between transmitting component 102 and receiving component 104. In practice, there are a plurality of bus lines, and each bus line might be connected to one or more transmitting components and/or one or more receiving components.

Within transmitting component 102, a current driver 108 generates a current I_(O) though bus line 106. The current driver is responsive to a logic level data signal 110 to switch the current driver on or off, generating a signal voltage V_(O). A high signal voltage is referred to as V_(OH), and is the result of switching the driver off. A low signal voltage is referred to as V_(OL), and is the result of switching the driver on. V_(OH) and V_(OL) are usually used to represent high and low binary logic levels “1” and “0”.

Receiving component 104 has a reference voltage VREF_(R) that can be independent of any voltage in transmitting component 102. VREF_(R) is generated by a digital-to-analog converter (DAC) 111. The DAC can be integrated with receiving component 104 or it can be separate from receiving component 104.

Receiver 104 includes a voltage comparator 112 that compares two analog voltage inputs and produces a binary voltage signal indicating which of the two input voltages is greater in magnitude. A comparator such as this is associated with each bus line to evaluate whether a logic signal represents a high or low logic voltage level.

One input of comparator 112 receives receiver reference voltage VREF_(R). The other input of comparator 112 is connected to bus line 106. In response to these two inputs, the comparator generates a logic level signal or voltage V_(D), representing a data bit or other information that has been transmitted from transmitting component 102. The value of V_(D) is dependent on whether V_(O) is greater or less than VREF_(R).

FIG. 5 illustrates a method of calibrating current driver 108 so that the resulting voltage swing V_(swing) is symmetrical around VREF_(R). Such a calibration is performed during system startup or during initialization of the transmitting and/or receiving components.

The method comprises varying the line drive current I_(O)—sequentially setting I_(O) to each of a range of possible values I_(O). This is accomplished by sequentially configuring the transmitting component's current driver 108 to supply line drive current I_(O) at a plurality of discrete values I_(O[)0]through I_(O)[n], as indicated in FIG. 5 by blocks 120 and 128.

Blocks 122 and 126 indicate an operation of varying the receiver reference voltage VREF_(R) through a predetermined sequence of different available voltages. This operation is repeated for every value of I_(O).

Operation 124 is performed for each VREF_(R) value, and comprises transmitting data from transmitting component 102 to receiving component 104 to find high and low receiver reference voltages at which data errors do not occur.

More specifically, operations 122, 124, and 126 comprise setting VREF_(R) to some intermediate value and then varying VREF_(R) downward. At each value of VREF_(R), the transmitting component sends worst-case test data and then determines whether or not there was an error in receiving the data at the receiving component. Initially, at intermediate voltages, errors are unlikely. However, as VREF_(R) is varied further downward, the margin between VREF_(R) and V_(OL) will become small enough to cause data errors. This establishes the low receiver reference voltage MVREF_(LO)—the lowest VREF_(R) at which data errors do not occur. A similar procedure, varying VREF_(R) in the upward direction, establishes MVREF_(HI)—the highest VREF_(R) at which data errors do not occur.

MVREF_(LO) and MVREF_(HI) are noted or recorded in arrays MVREF_(LO)[i] and MVREF_(HI)[i], corresponding to each drive current value I_(O)[i].

An operation 130 comprises examining or evaluating the noted high and low receiver reference voltages MVREF_(LO)[i] and MVREF_(HI)[i] corresponding to different drive currents I_(O)[i], to determine a desirable line drive current. More specifically, this operation comprises finding a pair of receiver reference voltages MVREF_(LO)[i] and MVREF_(HI)[i], for each value of i through n, that meet pre-specified criteria or are within specified parameters. Such predefined criteria, for example, might require that MVREF_(LO)[i] is less than some specified value and that MVREF_(HI)[i] is above some other specified value. Alternatively, the predefined criteria might specify that the desired drive current I_(O)[i] is obtained when V_(swing), the difference between MVREF_(HI)[i] and MVREF_(LO)[i], is at its greatest. This relationship produces the highest useful voltage margin at V_(OL). Another criteria might specify the drive current I_(O)[i] corresponding to the pair of MVREF_(LO)[i] and MVREF_(HI)[i] whose average (MVREF_(LO)[i]−MVREF_(HI)[i])/2) is closest to the VREF_(R) value that will be used during normal bus operation. This ensures that V_(OL) and V_(OH) are symmetrical around VREF_(R) during normal bus operation. Operation 132 comprises setting current driver 108 to the drive current I_(O)[i] corresponding to the pair of receiver reference voltages MVREF_(LO)[i] and MVREF_(HI)[i] that were found in operation 130. This drive current I_(O)[i] is used on all of the data signaling lines originating from transmitting component 102.

FIG. 6 shows a different embodiment of a system in which V_(OL) and V_(OH) are calibrated to provide symmetry at a receiving component. FIG. 6 shows only the current control and calibration circuitry in a transmitting component 198 and the comparison circuitry of a receiving component 199.

The current control and calibration circuitry of transmitting component 198 uses two different bus lines 202 and 203. A variable voltage divider 204 is located between the two bus lines. Divider 204 divides the voltage differential between a high line voltage V_(OH) and low line voltage V_(OL) to obtain an intermediate voltage V_(DIV) that is a dynamically programmable fraction between the high and low line voltages V_(OH) and V_(OL). The output voltage V_(DIV) of variable voltage divider 204 is controlled by a factor x stored in a symmetry control register 224: V_(DIV)=V_(OL)+x(V_(OH)−V_(OL)), where factor x is a value between 0 and 1.

The output V_(DIV) of the voltage divider is provided to a comparator 206, along with a transmitter reference voltage VREF_(T). VREF_(T) is generated by a DAC 207. The output feedback voltage V_(F) of the comparator is connected to control a current controller. Specifically, V_(F) drives the up/down count of a current control counter 208. The value of counter 208 is received by current drivers 212 (one associated with each bus line 202 and 203) to set or control the output line current I_(O), and, consequently, the line voltage V_(OL).

Up/down counter 208 is configured to control current drivers 212 only during a calibration operation. In normal bus operation, the current drivers' output I_(O) is controlled directly, by a current control register 213.

During normal bus operation, the current drivers are independently enabled and disabled in accordance with data signals (not shown) that indicate the data values that are to be transmitted. When enabled, a bus driver produces a line current I_(O) according to the value held in counter 208 or current control register 213, and a corresponding low line voltage V_(OL). When disabled, a bus driver produces no current and a corresponding high line voltage V_(OH), regardless of the value of counter 208 or current control register 213.

During normal bus operation, current control register 213 remains at a fixed value except for changes to account for temperature and power supply variations. Voltage divider 204, comparator 206, and symmetry control register 224 are not used during normal operation.

A calibration procedure is performed to determine appropriate values for current control register 224. During calibration, current drivers 212 are controlled by the output of up/down counter 208, rather than by current control register 213. The calibration process is performed at system startup or initialization, between a transmitter and every one of its possible receivers. During this process, bus line 202 is set to its high voltage V_(OH) by disabling the associated current driver 212. Bus line 203 is set to its low voltage V_(OL) by enabling the associated current driver 212.

The calibration circuit of FIG. 6 regulates drive current I_(O) to maintain V_(DIV) approximately equal to V_(REF). Thus, V_(DIV)=V_(REF) and V_(REF)=V_(OL)+x(V_(OH)−V_(OL)). If x=0.5, then, V_(REF) is halfway or 50% of the way between V_(OL) and V_(OH). If x=0.25, V_(REF) is 25% of the way from V_(OL) to V_(OH). Thus, factor x represents the location of V_(REF) as a fraction or percentage of the voltage range between V_(OL) and V_(OH).

In each receiving component 199, one of the bus lines 202/203 is connected to one input of a comparator 241. The other input of the comparator receives VREF_(R). VREF_(T) and VREF_(R) are controlled independently for the transmitting component and the receiving component. Thus, while one DAC 207 generates VREF_(T) for transmitter 198, a different programmable DAC 218 generates VREF_(R) for receiver 199. In FIG. 6, a separate DAC 218 is shown for every receiving component 199. However, some embodiments might use a single DAC to supply a common VREF_(R) to every receiving component.

The method of FIG. 5 is used in conjunction with the circuit of FIG. 6 to calibrate I_(O). In order to vary I_(O) during step 120, the factor x in symmetry control register 224 is cycled through its available values. Step 130 comprises determining the value of symmetry control register 224 that was used to produce the desired values of MVREF_(LO) and MVREF_(HI), and reloading this value into the symmetry control register 224 for future voltage/temperature calibrations. Step 132 comprises copying the counter value to the current control register 213 for subsequent use in normal operation of the bus lines.

During normal operation, voltage/temperature calibrations can be performed by continuously varying the value of current control register 213. In the described embodiment, however, a voltage/temperature calibration operation is performed every 10 milliseconds using the calibration circuitry already described. This operation involves activating voltage divider 204 and up/down counter 208 to control current drivers 212. Using the symmetry value found in step 130, the up/down counter is allowed to settle to a new value that maintains the originally determined degree of asymmetry with regard to VREF_(T). This new value is then loaded into current control register 213 for subsequent normal operation of the bus lines.

The circuits and methods described above allow transmitter drive currents to be optimized for each of a plurality of receivers. Furthermore, the calibration is performed dynamically, for actual pairs of transmitters and receivers. This method is more likely to produce optimum drive currents than the prior art method of predicting asymmetry values based on assumptions made during system design.

Although details of specific implementations and embodiments are described above, such details are intended to satisfy statutory disclosure obligations rather than to limit the scope of the following claims. Thus, the invention as defined by the claims is not limited to the specific features described above. Rather, the invention is claimed in any of its forms or modifications that fall within the proper scope of the appended claims, appropriately interpreted in accordance with the doctrine of equivalents. 

1. A receiving component for use in a system containing one or more data signaling lines and a transmitting component, the receiving component comprising: a comparator including: a data input for coupling to a data signaling line; and a receiver reference voltage input; and a variable reference voltage generator that generates a receiver reference voltage, the variable reference voltage generator coupled to the receiver reference voltage input; wherein the variable reference voltage generator is operative in a calibration mode to vary the receiver reference voltage while the comparator receives data from the data signaling line at the data input; wherein the receiving component is adapted to find high and low receiver reference voltages at which data errors do not occur.
 2. The receiving component as recited in claim 1, wherein the variable reference voltage generator comprises a digital-to-analog converter.
 3. The receiving component as recited in claim 1, wherein the variable reference voltage generator comprises circuitry operative to generate a reference voltage independent from voltages generated on the transmitting component.
 4. The receiving component as recited in claim 1, wherein the variable reference voltage generator is integrated with the comparator.
 5. The receiving component as recited in claim 1, wherein the variable reference voltage generator is separate from the comparator.
 6. The receiving component as recited in claim 1, wherein the data provided to the data input comprises a first analog voltage, and the receiver reference voltage comprises a second analog voltage; and wherein the comparator is adapted to compare the first and second analog voltages and to produce a binary voltage signal indicating which of the first and second analog voltages is greater in magnitude.
 7. The receiving component as recited in claim 6, wherein the binary voltage signal represents a data bit that has been transmitted from the transmitting component.
 8. The receiving component as recited in claim 1, wherein the data provided to the data input comprises a data input voltage; and wherein the comparator is adapted to produce a logic level signal that is dependent on whether the data input voltage is greater or less than the receiver reference voltage.
 9. The receiving component as recited in claim 1, wherein the receiving component comprises at least one peripheral device.
 10. The receiving component as recited in claim 9, wherein the at least one peripheral device comprises at least one of a memory device or a memory device controller.
 11. The receiving component as recited in claim 1, wherein the receiving component comprises a microprocessor.
 12. The receiving component as recited in claim 1, wherein the data received by the receiving component at the data input of the comparator is created by the transmitting component by driving a current on the data signaling line.
 13. The receiving component as recited in claim 12, wherein the driving of the current on the data signaling line causes a voltage change on the data signaling line and at the data input of the comparator.
 14. The receiving component as recited in claim 12, wherein the receiving component is further adapted to find high and low receiver reference voltages at which data errors do not occur for each current level of multiple current levels at which the transmitting component drives the data signaling line.
 15. The receiving component as recited in claim 1, wherein the receiving component is further adapted to analyze the high and low receiver reference voltages at which data errors do not occur to determine a desired drive current on the data signaling line for the transmitting component.
 16. A receiving device for use in a system containing one or more data signaling lines and a transmitting device, the receiving device comprising: comparison means for comparing two values, the comparison means including: a data input for coupling to a data signaling line; and a receiver reference voltage input; and variable voltage generating means for generating a receiver reference voltage, the variable voltage generating means coupled to the receiver reference voltage input; wherein the variable voltage generating means is operative in a calibration mode to vary the receiver reference voltage while the comparison means receives data from the data signaling line at the data input; wherein the receiving device is adapted to find high and low receiver reference voltages at which data errors do not occur.
 17. The receiving device as recited in claim 16, wherein the variable voltage generating means comprises a conversion means for converting a digital signal to an analog signal.
 18. The receiving device as recited in claim 16, wherein the variable voltage generating means comprises circuitry operative to generate a reference voltage independent from voltages generated on the transmitting device.
 19. The receiving device as recited in claim 16, wherein the variable voltage generating means is integrated with the comparison means.
 20. The receiving device as recited in claim 16, wherein the variable voltage generating means is separate from the comparison means.
 21. The receiving device as recited in claim 16, wherein the data provided to the data input comprises a first analog voltage value, and the receiver reference voltage comprises a second analog voltage value; and wherein the comparison means is adapted to compare the first and second analog voltage values and to produce a binary voltage signal indicating which of the first and second analog voltage values is greater in magnitude.
 22. The receiving device as recited in claim 21, wherein the binary voltage signal represents a data bit that has been transmitted from the transmitting device.
 23. The receiving device as recited in claim 16, wherein the data provided to the data input comprises a data input voltage value; and wherein the comparator is adapted to produce a logic level signal that is dependent on whether the data input voltage value is greater or less than the receiver reference voltage value.
 24. The receiving device as recited in claim 16, wherein the receiving device comprises at least one peripheral device.
 25. The receiving device as recited in claim 24, wherein the at least one peripheral device comprises at least one of a memory device or a memory device controller.
 26. The receiving device as recited in claim 16, wherein the receiving device comprises a microprocessor.
 27. The receiving device as recited in claim 16, wherein the data received by the receiving device at the data input of the comparison means is created by the transmitting device by driving a current on the data signaling line.
 28. The receiving device as recited in claim 27, wherein the driving of the current on the data signaling line causes a voltage change on the data signaling line and at the data input of the comparison means.
 29. The receiving device as recited in claim 27, wherein the receiving device is further adapted to find high and low receiver reference voltages at which data errors do not occur for each current level of multiple current levels at which the transmitting device drives the data signaling line.
 30. The receiving device as recited in claim 16, wherein the receiving device is further adapted to analyze the high and low receiver reference voltages at which data errors do not occur to determine a desired drive current on the data signaling line for the transmitting device.
 31. At least one computer-readable medium having stored thereon a data structure defining a receiving component, the data structure comprising: first data representing a comparator, the first data defining the comparator to include: an input node for coupling to a signaling line, and a receiver reference voltage input; and second data representing a variable reference voltage generator that generates a receiver reference voltage, the second data defining the variable reference voltage generator to be coupled to the receiver reference voltage input; wherein the variable reference voltage generator is operative in a calibration mode to vary the receiver reference voltage while the comparator receives a signal from the signaling line at the input node; wherein the receiving component is adapted to find high and low receiver reference voltages at which errors do not occur.
 32. The at least one computer-readable medium as recited in claim 31, wherein the second data defines the variable reference voltage generator to include a digital-to-analog converter.
 33. The at least one computer-readable medium as recited in claim 31, wherein the second data defines the variable reference voltage generator to include circuitry operative to generate a reference voltage independent from voltages generated on a transmitting component, the transmitting component and the receiving component defined as forming at least part of a communications system.
 34. The at least one computer-readable medium as recited in claim 31, wherein the first and second data define the variable reference voltage generator as being integrated with the comparator.
 35. The at least one computer-readable medium as recited in claim 31, wherein the first and second data define the variable reference voltage generator as being separate from the comparator.
 36. The at least one computer-readable medium as recited m claim 31, wherein the signal provided to the input node comprises a first analog voltage, and the receiver reference voltage comprises a second analog voltage, and wherein the comparator is adapted to compare the first and second analog voltages and to produce a binary voltage signal indicating which of the first and second analog voltages is greater in magnitude.
 37. The at least one computer-readable medium as recited in claim 36, wherein the binary voltage signal represents a bit that has been transmitted from a transmitting component, the transmitting component and the receiving component defined as forming at least part of a communications system.
 38. The at least one computer-readable medium as recited in claim 31, wherein the signal provided to the input node comprises an input voltage; and wherein the comparator is adapted to produce a logic level signal that is dependent on whether the input voltage is greater or less than the receiver reference voltage.
 39. The at least one computer-readable medium as recited in claim 31, wherein the receiving component is defined as comprising at least one peripheral device.
 40. The at least one computer-readable medium as recited in claim 31, wherein the receiving component is defined as comprising at least one of a memory device or a memory device controller.
 41. The at least one computer-readable medium as recited in claim 31, wherein the receiving component is defined as comprising a microprocessor.
 42. The at least one computer-readable medium as recited in claim 31, wherein the signal received by the receiving component at the input node of the comparator is created by a transmitting component by driving a current on the signaling line, the transmitting component and the receiving component defined as forming at least part of a data communications system.
 43. The at least one computer-readable medium as recited in claim 42, wherein the driving of the current on the signaling line causes a voltage change on the signaling line and at the input of the comparator.
 44. The at least one computer-readable medium as recited in claim 42, wherein the receiving component is further adapted to find high and low receiver reference voltages at which errors do not occur for each current level of multiple current levels at which the transmitting component drives the signaling line.
 45. The at least one computer-readable medium as recited in claim 31, wherein the receiving component is further adapted to analyze the high and low receiver reference voltages at which errors do not occur to determine a desired drive current on the signaling line for a transmitting component, the transmitting component and the receiving component defined as forming at least part of a data communications system. 